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Explainer14 min

Noise, and where the microvolt goes

Thermal, 1/f, amplifier, and electrode noise, added up for a real EEG channel. Why the electrode dominates, why the breadboard was so bad, and how to read a noise floor.

On this page14 min
  1. Every resistor hisses
  2. The amplifier adds two kinds
  3. The low-frequency rise
  4. Adding them up
  5. Why the breadboard was so bad
  6. Reading a noise floor

You measured a with the inputs shorted, and a worse one with in the . The difference is the . Let’s account for every microvolt: where noise comes from, how sources add, and why in a well-designed system the chip is rarely the limit.

Every resistor hisses

A resistor at room temperature produces a random voltage across itself just from the thermal motion of its electrons. The RMS value is √(4 k T R Δf): Boltzmann’s constant, temperature, resistance, bandwidth. For 10 kΩ over a 40 Hz bandwidth at body temperature that is about 80 nV RMS. For 1 MΩ, about 800 nV. This is and there is no circuit trick that removes it; there is only lowering the resistance or the bandwidth or the temperature.

An with an impedance of 50 kΩ at 10 Hz is, for noise purposes, a 50 kΩ resistor: about 180 nV RMS over the band, per , and there are two in every measurement. A at 1 MΩ is 800 nV each. That is already most of a microvolt before the amplifier has done anything.

The amplifier adds two kinds

A voltage noise, quoted in nanovolts per root hertz, which for a good is 8 to 10 nV/√Hz, so about 60 nV RMS over 40 Hz. Negligible against the . And a current noise, in femtoamps or picoamps per root hertz, which flows through the and becomes a voltage: current noise times impedance. For the INA128’s 0.3 pA/√Hz through a 50 kΩ that is 15 nV/√Hz, comparable to its voltage noise; through a 1 MΩ it is 300 nV/√Hz, which dominates everything. This is why chips meant for are chosen for low current noise.

The low-frequency rise

Below a few hertz, every amplifier and every gets noisier, following roughly one over frequency. This comes from slow fluctuations in materials, in the chip’s transistors and in the ’s chemistry. It is why the you measured is dominated by slow wander, why a 0.5 Hz high-pass makes the trace look so much cleaner, and why sub-hertz (which exists and is interesting) is hard to record.

Adding them up

Independent noise sources add as the square root of the sum of squares, not directly. Two 180 nV and a 60 nV amplifier: √(180² + 180² + 60²) ≈ 260 nV. The biggest source dominates; halving a small source does almost nothing. This is the arithmetic that tells you where to spend effort: a 1 µV-noise chip replaced by a 0.5 µV chip does nothing if the contribute 2 µV.

Figure 1. Where the microvolt goes, over the 0.5 to 40 Hz band. Read it as a budget: the top entry sets the total almost by itself, and every hour spent on anything below it buys nothing.
Predict before you look

Your shorted-input noise floor is 0.8 µV RMS. With electrodes in the phantom it is 2.1 µV RMS. What are the electrodes contributing?

About 1.9 µV. Independent sources add in quadrature: √(2.1² − 0.8²) = √(4.41 − 0.64) ≈ 1.94 µV. The are contributing more than twice what the electronics do, which is the normal situation, and it tells you that better , not a better chip, is the next improvement.

Why the breadboard was so bad

None of the above explains a of 15 µV, which is what a breadboarded amplifier typically shows. That is not thermal noise; it is pickup. Long, springy, unshielded connections at a high-impedance node act as antennas for the room’s electric field, and the resulting voltage is far larger than any thermal source. The cure is short, soldered, and, for the input node, guarded. That is why the of the same circuit falls by a factor of five when it moves from breadboard to soldered board, and why the layout rules exist.

Reading a noise floor

Report it as RMS in microvolts over a stated bandwidth, input-referred, with the inputs shorted at the connector. “0.9 µV RMS, 0.5 to 40 Hz, 24, 250 SPS” is a complete statement; “low noise” is not. Also report peak-to-peak, which is roughly six times RMS for Gaussian noise and is what you see on the trace. And plot the noise : its shape tells you which source dominates. A flat floor is thermal or amplifier noise; a rise at low frequency is 1/f; a is pickup at that frequency.

Deep dive Noise density versus RMS 3 min

quote noise as a density in nV/√Hz because the RMS value depends on bandwidth. To convert, multiply by the square root of the bandwidth: 8 nV/√Hz over 40 Hz is 8 × 6.3 ≈ 50 nV RMS. For a 1/f source the integral is a logarithm and the low cutoff matters; that is why “from 0.1 Hz” and “from 1 Hz” noise figures differ so much.

Deep dive Why gain helps with noise, up to a point 3 min

The converter has its own noise, referred to its input. An amplifier of G in front of it divides that noise by G when referred to the . So more makes the converter’s noise matter less, until the signal plus offsets threaten to exceed the converter’s range. That trade sets the of 24 in the for . For , whose signals are bigger, a lower is used and the converter’s noise contributes more, which is acceptable because is bigger.

Deep dive Averaging and the square root of N 2 min

Noise that is independent from trial to trial shrinks as the square root of the number of trials averaged. That is the whole basis of the event-related potential, which Phase 3 is about: a 5 µV response in 20 µV of noise is invisible in one trial and clear in a hundred. The after averaging is the single-trial ratio times √N.

Recall
How do independent noise sources combine, and what does that imply for design effort?
As the square root of the sum of squares. The largest source dominates, so effort spent shrinking a small source is wasted until the big one is reduced.
Recall
Why does a dry electrode make the amplifier's current noise matter?
Current noise flows through the electrode impedance and becomes voltage noise; with a megohm electrode, even a fraction of a picoamp per root hertz produces hundreds of nanovolts per root hertz.
Recall
What is a complete statement of a noise floor?
RMS in microvolts, over a stated bandwidth, input-referred, with the inputs shorted at the connector, at the stated gain and sample rate. For example, 0.9 µV RMS, 0.5 to 40 Hz, gain 24, 250 SPS.
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